Method and apparatus for pulse width modulation

ABSTRACT

An apparatus and method of providing a pulse width modulated signal that is responsive to a current are disclosed. A circuit according to aspects of the present invention includes a capacitor to convert a first current to a first voltage on the capacitor during a first time duration and to discharge a second current from the capacitor to change the first voltage to a second voltage during a second time duration. A comparator is also included and is coupled to an output of the capacitor to compare a voltage on the capacitor to a reference voltage during the second time duration to change a pulse width of a periodic output signal in response to an input current.

REFERENCE TO PRIOR APPLICATION

This application is a continuation of U.S. application Ser. No. 12/608,845, filed Oct. 29, 2009, now pending, which is a continuation of and claims priority to U.S. application Ser. No. 11/543,503, filed Oct. 4, 2006, now issued U.S. Pat. No. 7,629,823 entitled, “Method and Apparatus for Pulse Width Modulation.” U.S. application Ser. No. 12/608,845 and U.S. Pat. No. 7,629,823 are hereby incorporated by reference.

BACKGROUND INFORMATION Field of the Disclosure

The present invention relates generally to power supplies and, more specifically, the present invention relates to a pulse width modulator circuit.

BACKGROUND

Many switching power supplies use pulse width modulation to regulate an output. A pulse width modulator receives a control signal that is related to the value of the output. The pulse width modulator then sets the conduction time of the switch as a fraction of a switching period according to the value of the control signal. The fraction of the switching period that is the conduction time is the duty ratio of the switch.

The change in duty ratio in response to a change in control signal is a measure of the gain of the pulse width modulator. The gain of the modulator is typically well controlled because the gain has a strong influence on the stability and the dynamic response of the system.

Traditional pulse width modulators use a voltage comparator to compare a control voltage to a triangular or sawtooth voltage from an oscillator. The output of the comparator is the pulse width modulated signal. In applications where the control signal is a current instead of a voltage, a resistor converts the current to a voltage for input to the comparator. The value of the resistor is typically well controlled because it is directly proportional to the gain of the modulator. A problem arises when the traditional technique is used in integrated circuits because it is expensive to implement an integrated resistor with a precise value that does not change with temperature and variations in the process of fabrication.

BRIEF DESCRIPTION OF THE DRAWINGS

Non-limiting and non-exhaustive embodiments of the present invention are described with reference to the following figures, wherein like reference numerals refer to like parts throughout the various views unless otherwise specified.

FIG. 1 is a block diagram illustrating generally an example duty ratio control circuit in accordance with the teachings of the present invention.

FIG. 2 is a graph illustrating generally a response of a pulse width modulator circuit of an example duty ratio control circuit in accordance with the teachings of the present invention.

FIG. 3 is a schematic diagram illustrating generally an example duty ratio control circuit that produces the response of the graph in FIG. 2 in accordance with the teachings of the present invention.

FIG. 4 is a diagram illustrating generally timing relationships of signals in the duty ratio control circuit of FIG. 3.

FIG. 5 is a schematic diagram illustrating generally a duty ratio control circuit in accordance with the teachings of the present invention; and

FIG. 6 is a schematic diagram illustrating generally another duty ratio control circuit in accordance with the teachings of the present invention.

FIG. 7 is a diagram illustrating generally timing relationships of signals in the duty ratio control circuit of FIG. 6 in accordance with the teachings of the present invention.

DETAILED DESCRIPTION

Methods and apparatuses for providing a pulse width modulated signal that is responsive to a current. In the following description numerous specific details are set forth in order to provide a thorough understanding of the present invention. It will be apparent, however, to one having ordinary skill in the art that the specific detail need not be employed to practice the present invention. In other instances, well-known materials or methods have not been described in detail in order to avoid obscuring the present invention.

Reference throughout this specification to “one embodiment” or “an embodiment” means that a particular feature, structure or characteristic described in connection with the embodiment is included in at least one embodiment of the present invention. Thus, appearances of the phrases “in one embodiment” or “in an embodiment” in various places throughout this specification are not necessarily all referring to the same embodiment. Furthermore, the particular features, structures or characteristics may be combined in any suitable combinations and/or subcombinations in one or more embodiments. In addition, it is appreciated that the figures provided herewith are for explanation purposes to persons ordinarily skilled in the art and that the drawings are not necessarily drawn to scale.

In various examples of circuits according to the teachings of the present invention, a pulse width modulated signal that is responsive to a current is provided. Example methods include features that may be beneficial for use in integrated circuits. In particular, example circuits in accordance with the teachings of the present invention may be useful in integrated circuits that control switching power supplies.

In one aspect of the invention, there may be substantially no dependence on the value of a resistor to convert a control current to a pulse width modulated signal. Instead, according to various examples, the method uses a current proportional to the control current to charge a capacitor for a known time within the period of an oscillator. A known current then discharges the capacitor. The time for the voltage on the capacitor to go from its initial value to a reference voltage determines the duty ratio as a fraction of the period of the oscillator in accordance with the teachings of the present invention.

In this way, the nature of example circuits makes the duty ratio independent of the value of the capacitor, or for example the value of a reference voltage, or for example the delay of a comparator, or for example the value of another circuit element such as for example the value of a resistor. When used in an integrated circuit, it is easy to trim the currents to obtain the desired precision of parameters. Another aspect of examples of the present invention includes allowing a mode of modulation to change among constant on-time, constant off-time, and constant frequency modes while maintaining a constant modulator gain.

To illustrate, FIG. 1 is a block diagram that illustrates generally one example duty ratio circuit in accordance with the teachings of the present invention. As shown, a duty ratio control circuit 100 includes a pulse width modulator circuit 110 and an oscillator 150. As shown in FIG. 1, one example of duty ratio control circuit 100 is included in an integrated circuit that is coupled to control a power supply 102. The pulse width modular circuit 110 receives a timing signal U_(osc) 140 from the oscillator 150 to produce a pulse width modulated signal 130 that is a voltage V_(PWM) in the example of FIG. 1. Timing signal U_(osc) 140 may be either a voltage or a current. In the example, timing signal U_(osc) 140 is periodic with a period T_(osc). Timing signal U_(osc) is low for a fraction k of period T_(osc) and is high for the remainder of period T_(osc). Pulse width modulated signal 130 is high for a fraction D of period T_(osc), where D is the duty ratio. The pulse width modulator circuit 110 also receives a control current I_(C) 120. In one example, control current I_(C) 120 adjusts the duty ratio D.

FIG. 2 is a graph illustrating generally a desired response of a pulse width modulator circuit in accordance with the teachings of the present invention. The graph 200 shows how a duty ratio D changes in response to a control current I_(C). In the example, the duty ratio D is a maximum value D_(B) for control current less than I_(B), and a minimum value D_(A) for control current greater than I_(A). The duty ratio is a value D_(X) that is between D_(A) and D_(B) when the control current is a value I_(X) that is between I_(A) and I_(B). The gain of the pulse width modulator between control currents I_(A)and I_(B) is the slope -m. The pulse width modulator gain m in the example of FIG. 2 has the units of reciprocal amperes.

FIG. 3 is a schematic diagram of one example of a duty ratio control circuit 300 that produces the response similar to graph 200 in accordance with the teachings of the present invention. As shown, the circuit 300 receives control current I_(C) 120. A current source 305 subtracts a current I_(s) from control current I_(C) 120. The difference between control current I_(C) 120 and current I_(s) from control current 305 is received by transistor 310 at the input of current mirror 352. Transistors 310 and 315 of current mirror 352 have strengths in the respective ratio of 1:M so that the mirrored current 325 is the input current multiplied by the scale factor M.

In the example of FIG. 3, oscillator 150 provides a timing signal 340 that controls a switch S₁ 378. When the timing signal 340 is low, switch S₁ 378 closes to charge a capacitor C_(D) 376 with a current that is the sum of current I₁ from current source 345 and the current through rectifier 354. Current through a rectifier 354 is the difference between the current from current source 335 and the mirrored current 325 when the difference is positive. Current through rectifier 354 is zero when the mirrored current 325 is greater than the current from current source 335. In one example, rectifier 354 includes a diode.

Voltage V_(D) 356 on capacitor C_(D) 376 is compared to a reference voltage V_(REF) 372 by a comparator 360. The output 370 of comparator 360 is high when voltage V_(D) 356 is greater than reference voltage V_(REF) 372. The output 370 of comparator 360 is low when voltage V_(D) 356 is less than reference voltage V_(REF) 372.

As shown in the illustrated example, a delaying circuit 366 is coupled to delay the rising edge of the signal from oscillator 150. In the example, delaying circuit 366 is included to compensate for a non-ideal response of comparator 360 that in one example may be a delay in the response of comparator 360. A delayed timing signal 358 from delaying circuit 366 and output 370 of comparator 360 are received as inputs to an AND gate 362. The output 374 of AND gate 362 controls a switch S₂ 384. The output of AND gate 362 is also the pulse width modulated signal 330. When the output 374 of AND gate 362 is high, switch S₂ closes to discharge capacitor C_(D) 376 with current source 382.

FIG. 4 illustrates example timing relationships of three signals in the duty ratio control circuit example of FIG. 3. In the example, FIG. 4 shows a timing signal 340 received by the pulse width modulator circuit from oscillator 150, an example diagram of voltage V_(D) 356 on capacitor C_(D) 376, and an example pulse width modulated signal 330 produced by circuit 300. When the example circuit 300 of FIG. 3 operates, voltage V_(D) 356 increases from a value V_(REF) to a value V_(FB) as capacitor C_(D) 376 charges during a time that is a fraction k of the period T_(osc) of timing signal 340. The fraction k may be chosen to set a substantially guaranteed limit on the maximum duty ratio from the pulse width modulator, since the output or signal 330 of the pulse width modulator must be low for substantially the same duration as the fraction k of the period T_(osc).

Capacitor C_(D) 376 charges with current I₁ from current source 345 added to the current in rectifier 354. Capacitor C_(D) will charge with current I₁ when the control current I_(C) 120 is large enough to make the current in rectifier 354 zero. The value of current I₁ is therefore chosen in one example to guarantee that the pulse width modulator signal 330 is high for a minimum duration during each period of the timing signal 340 from oscillator 150.

After the timing signal 340 from oscillator 150 goes high, the voltage V_(D) 356 on capacitor C_(D) 376 remains at a value V_(FB) during the delay T_(DELAY) from delaying circuit 366. After the delay T_(DELAY) from delaying circuit 366, current source 382 discharges capacitor C_(D) 376 with a fraction Q of a reference current I₀.

As can be seen in the illustrated example, pulse width modulator signal 330 is high while capacitor C_(D) 376 discharges from the voltage V_(FB) to voltage V_(REF). In the example, the fraction Q of the reference current I₀ is a multiplier less than one that may be selected along with the selection of the values of the multiplier P, the fraction k, and the current I₁ as an adjustment on the discharge current from capacitor C_(D) 376 to reduce the discharge current sufficiently to substantially guarantee that the maximum duty ratio is determined by the timing signal 340 from oscillator 150. In some examples, it may be desirable to have the oscillator 150 dominate the timing relationships in examples where the frequency of the oscillator is a trimmed parameter of an integrated circuit. Thus, in the example, duty ratio D is the fraction of the period T_(osc) of oscillator 150 that corresponds to either the time duration while capacitor C_(D) 376 is discharging from the value V_(FB) to the value V_(REF), or the time duration of a high level of timing signal 340, whichever is less.

The duty ratio D and the slope m of the pulse width modulator or PWM gain are given for I_(A)>I_(C)>I_(B) by the expressions

$D = {\frac{k}{Q\; I_{0}}\left\lbrack {{P\; I_{0}} + I_{1} - {M\left( {I_{C} - I_{B}} \right)}} \right\rbrack}$ $m = \frac{M\; k}{Q\; I_{0}}$

where I₀ is a bias current that may be selected from considerations of power dissipation or other design rules for an integrated circuit. In one example, current I₁ 345 is selected to determine a minimum duration for the pulse width modulator signal 330 to be high in applications that may require it. The fraction k determines the maximum duty ratio. In one example, the multiplier P of current source 335 in FIG. 3 is chosen to be

$P = {\frac{1}{k} - 1}$

Therefore, the duty ratio D is independent of the value of the capacitor C_(D) 376 or for example a reference voltage or for example another circuit element such as for example the value of a resistor. Although the duty ratio D and the slope m of the PWM gain are independent of the value of capacitor C_(D) 376, the value and type of capacitor C_(D) 376 are selected in various examples to meet the environmental requirements of the application. Parameters Q, M, and I₀ may be adjusted accordingly.

In one example, T_(osc) is 7.58 μs corresponding to an oscillator frequency of 132 kHz, for which the other parameters are k=0.2, P=4, Q=0.975, I₀=10 μA, I=610 nA, M=11.21×10⁻³, and the delay time T_(DELAY) of rising edge delaying circuit 366 in FIG. 3 is 150 ns.

FIG. 5 shows an example of a duty ratio control circuit 500 where a control logic 530 receives timing signal 340 from oscillator 150, output 370 of comparator 360, and other signals 510 from the system to control oscillator 150 as well as the switching of switches S₁ 378 and S₂ 384 that charge and discharge capacitor C_(D) 376 in accordance with teachings of the invention. In the example, control logic 530 can thus allow a pulse width modulator signal 330 to change its frequency as well as its duty ratio in response to system input(s) 510 from an external system in accordance with the teachings of the present invention.

FIG. 6 shows an example circuit of a duty ratio control circuit 600 including additional switches S_(J) 625 and S_(K) 615 with respective current sources 620 and 605 having respective currents I_(J) and I_(K) to charge and discharge capacitor C_(D) 376, the switching responding to control logic 530 in accordance with teachings of the invention. In one example, control logic 530 causes signals 610 and 630 to switch switches S_(K) 615 and S_(J) 625 respectively. An output 520 from control logic 530 changes the frequency of the oscillator 150 according to the state of the output to the output 370 of comparator 360.

FIG. 7 illustrates generally one example of the use of switches S_(k) 615 and S_(J) 625 to alter the charging and discharging of the capacitor C_(D) 376. Line segment 710 shows an increase in the voltage V_(D) 635 for a time T_(K) while switch S_(K) 615 is closed. Line segment 720 shows the voltage V_(D) 635 held constant at a value between V_(REF) and V_(FB) for a time T_(H) while all switches are open. Line segment 730 shows the voltage V_(D) 635 decreasing for a time T_(J) while switch S_(J) 625 is closed. Control logic 530 responds to the output of comparator 360 to cause the output 340 of oscillator 150 to remain high during the times T_(K), T_(H), and T_(J), thereby increasing the period of the oscillator 150 from a first value T_(osc1) to a second value T_(osc2). Thus, the pulse width modulator may contain a plurality of switches and current sources to charge and discharge a capacitor such as capacitor C_(D) 376 in response to a plurality of inputs 510. The additional switches and current sources may modify the response of the pulse width modulator signal 330 to control current I_(C) 120 depending on the needs of the system.

The above description of illustrated examples of the present invention, including what is described in the Abstract, are not intended to be exhaustive or to be limitation to the precise forms disclosed. While specific embodiments of, and examples for, the invention are described herein for illustrative purposes, various equivalent modifications are possible without departing from the broader spirit and scope of the present invention. Indeed, it is appreciated that the specific voltages, currents, frequencies, power range values, times, etc., are provided for explanation purposes and that other values may also be employed in other embodiments and examples in accordance with the teachings of the present invention.

These modifications can be made to examples of the invention in light of the above detailed description. The terms used in the following claims should not be construed to limit the invention to the specific embodiments disclosed in the specification and the claims. Rather, the scope is to be determined entirely by the following claims, which are to be construed in accordance with established doctrines of claim interpretation. The present specification and figures are accordingly to be regarded as illustrative rather than restrictive. 

1. An integrated control circuit, comprising: a capacitor coupled to develop a first voltage during a first time duration in response to a charge current received by the capacitor and to develop a second voltage during a second time duration in response to a discharge current provided by the capacitor and wherein the charge current is generated in response to a control signal; a comparator coupled to the capacitor to generate an output indicating when the capacitor reaches the second voltage; and a control logic that is coupled to output a periodic output signal, wherein the control logic sets a duty ratio of the periodic output signal in response to a time that it takes the capacitor to discharge from the first voltage to the second voltage.
 2. The integrated control circuit of claim 1 wherein the pulse width of the periodic output signal is substantially independent of the value of the capacitor.
 3. The integrated control circuit of claim 1 wherein the pulse width of the periodic output signal is substantially independent of the value of the second voltage.
 4. The integrated control circuit of claim 1 wherein the pulse width of the periodic output signal is substantially independent of a delay in the response of the comparator.
 5. The integrated control circuit of claim 1 wherein the pulse width of the periodic output signal is substantially independent of the value of a resistor.
 6. The integrated control circuit of claim 1 wherein a change in capacitor voltage terminates when the voltage on the capacitor reaches the second voltage during the second time duration.
 7. The integrated control circuit of claim 1, further comprising an oscillator coupled to provide a timing signal to the control logic, wherein a period of the periodic output signal is a period of the timing signal.
 8. The integrated control circuit of claim 7, wherein the timing signal received from the oscillator determines a maximum on-time of the periodic output signal.
 9. The integrated control circuit of claim 7, wherein the control logic includes an output that is coupled to the oscillator to change a frequency of the oscillator.
 10. The integrated control circuit of claim 7, wherein the control logic changes the frequency of the oscillator in response to the output of the comparator.
 11. The integrated control circuit of claim 7, wherein the control logic is to be coupled to receive at least one system input from an external system to change a frequency of the periodic output signal. 